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TM
MP1593
3A, 28V, 385KHz Step-Down Converter
The Future of Analog IC Technology
TM
DESCRIPTION
The MP1593 is a step-down regulator with an internal Power MOSFET. It achieves 3A of continuous output current over a wide input supply range with excellent load and line regulation. Current mode operation provides fast transient response and eases loop stabilization. Fault condition protection includes cycle-by-cycle current limiting and thermal shutdown. An adjustable soft-start reduces the stress on the input source at startup. In shutdown mode the regulator draws 20A of supply current. The MP1593 requires a minimum number of readily available external components, providing a compact solution.
FEATURES
* * * * * * * * * * * * * * * * * * * * 3A Output Current Programmable Soft-Start 100m Internal Power MOSFET Switch Stable with Low ESR Output Ceramic Capacitors Up to 95% Efficiency 20A Shutdown Mode Fixed 385KHz Frequency Thermal Shutdown Cycle-by-Cycle Over Current Protection Wide 4.75V to 28V Operating Input Range Output Adjustable from 1.22V Under-Voltage Lockout Available in 8-Pin SOIC Package Distributed Power Systems Battery Chargers Pre-Regulator for Linear Regulators Flat Panel TVs Set-Top Boxes Cigarette Lighter Powered Devices DVD/PVR Devices
APPLICATIONS
EVALUATION BOARD REFERENCE
Board Number EV1593DN-00A Dimensions 2.1"X x 1.3"Y x 0.4"Z
"MPS" and "The Future of Analog IC Technology" are Trademarks of Monolithic Power Systems, Inc.
TYPICAL APPLICATION
INPUT 4.75V to 28V
2 IN 7 EN 8 1 BS 3 SW
C5 10nF
100 95
Efficiency vs Load Current
VIN = 9V VIN = 24V VIN = 12V
OUTPUT 3.3V 3A
90
EFFICIENCY (%)
OFF ON
MP1593
SS GND 4 FB COMP 6
85 80 75 70 65 60 55 50 0 0.5 1.0
5
C6
(optional)
C3 8.2nF
D1 B340A
1.5
2.0
2.5
3.0
3.5
LOAD CURRENT (A)
MP1593 Rev. 1.9 9/14/2006
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MP1593 - 3A, 28V, 385KHz STEP-DOWN CONVERTER
PACKAGE REFERENCE
TOP VIEW
BS IN SW GND 1 2 3 4 8 7 6 5 SS EN COMP FB
ABSOLUTE MAXIMUM RATINGS (1)
Supply Voltage VIN ....................... -0.3V to +30V Switch Voltage VSW .............. -0.5V to VIN + 0.3V Boost Voltage VBS ..........VSW - 0.3V to VSW + 6V All Other Pins................................. -0.3V to +6V Junction Temperature...............................150C Lead Temperature ....................................260C Storage Temperature .............-65C to +150C
Recommended Operating Conditions
(2)
EXPOSED PAD ON BACKSIDE CONNECT TO PIN 4
Input Voltage VIN ............................ 4.75V to 28V Ambient Operating Temp............. -40C to +85C
Thermal Resistance
Part Number* MP1593DN * Package SOIC8E (Exposed Pad) Temperature -40C to +85C
(3)
SOIC8E (Exposed Pad).......... 50 ...... 10... C/W
Notes: 1) Exceeding these ratings may damage the device. 2) The device is not guaranteed to function outside of its operating conditions. 3) Measured on approximately 1" square of 1 oz copper.
JA
JC
For Tape & Reel, add suffix -Z (eg. MP1593DN-Z) For RoHS Compliant Packaging, add suffix -LF (eg. MP1593DN-LF-Z)
ELECTRICAL CHARACTERISTICS
VIN = 12V, TA = +25C, unless otherwise noted.
Parameter Shutdown Supply Current Supply Current Feedback Voltage Error Amplifier Voltage Gain Error Amplifier Transconductance High-Side Switch On-Resistance Low-Side Switch On-Resistance High-Side Switch Leakage Current Current Limit Current Sense to COMP Transconductance Oscillation Frequency Short Circuit Oscillation Frequency Maximum Duty Cycle Minimum Duty Cycle Symbol Condition VEN = 0V VEN = 2.6V, VFB = 1.4V VFB AEA GEA RDS(ON)1 RDS(ON)2 VEN = 0V, VSW = 0V 4.8 GCS fOSC1 fOSC2 DMAX DMIN VFB = 0V VFB = 1.0V VFB = 1.5V 335 25 ICOMP = 10A 500 4.75V VIN 28V VCOMP < 2V Min Typ 20 1.0 1.222 400 800 100 10 0 6.2 5.4 385 45 90 0 435 60 10 7.6 1120 140 Max 30 1.2 1.250 Units A mA V V/V A/V m A A A/V KHz KHz % %
1.194
MP1593 Rev. 1.9 9/14/2006
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MP1593 - 3A, 28V, 385KHz STEP-DOWN CONVERTER
ELECTRICAL CHARACTERISTICS (continued)
VIN = 12V, TA = +25C, unless otherwise noted.
Parameter EN Threshold Voltage Enable Pull Up Current Under-Voltage Lockout Threshold Under-Voltage Lockout Threshold Hysteresis Soft-Start Period Thermal Shutdown Symbol Condition VEN = 0V VIN Rising Min 0.9 1.0 2.3 Typ 1.2 1.7 2.6 210 CSS = 0.1F 10 160 Max 1.5 2.5 2.9 Units V A V mV ms C
TYPICAL PERFORMANCE CHARACTERISTICS
Refer to Typical Application Schematic on Page 1
Feedback Voltage vs Temperature
1.245 1.235 1.225 1.215 1.205 1.195 -60 -40 -20 0 20 40 60 80 100 120 140 5.0
Peak Current Limit vs Temperature
PEAK CURRENT LIMIT (A)
4.9 4.8 4.7 4.6 4.5 4.4 4.3 4.2 4.1 4.0 -50 -25 -0 25 50 75 100 125 150
Oscillation Frequency vs Temperature
OSCILLATION FREQUENCY (KHz)
420 410 400 390 380 370 360 350 340 -60 -40 -20 0 20 40 60 80 100 120 140
FEEDBACK VOLTAGE (V)
TEMPERATURE (C)
TEMPERATURE (C)
TEMPERATURE (C)
Soft-Start Waveforms
Turn Off Waveforms
VOUT 1V/Div.
Load Transient Waveforms
VOUT 100mV/Div.
VOUT 1V/Div.
IL 1A/Div.
IL 1A/Div.
IL 1A/Div.
4ms/Div. VIN = 12V, VOUT = 3.3V, 1A - 2A STEP
MP1593 Rev. 1.9 9/14/2006
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MP1593 - 3A, 28V, 385KHz STEP-DOWN CONVERTER
TYPICAL PERFORMANCE CHARACTERISTICS (continued)
Refer to Typical Application Schematic on Page 1
Switching Waveforms
IL 1A/Div.
100 95 90
Efficiency vs Load Current
100
Efficiency vs Load Current
95 90
VIN = 5V
VIN = 9V VIN = 24V VIN = 12V
EFFICIENCY (%)
EFFICIENCY (%)
VOUT 10mV/Div. VIN 100mV/Div. VSW 10V/Div.
85 80 75 70 65 60 55 50 0 500 1000 1500 2000 2500 3000 3500
85 80 75 70 65 60 55 50 0
VIN = 24V VIN = 12V
500 1000 1500 2000 2500 3000 3500
LOAD CURRENT (mA)
LOAD CURRENT (mA)
PIN FUNCTIONS
Pin # Name Description 1 2 High-Side Gate Drive Boost Input. BS supplies the drive for the high-side N-Channel MOSFET switch. Connect a 10nF or greater capacitor from SW to BS to power the high-side switch. Power Input. IN supplies power to the IC. Drive IN with a 4.75V to 28V power source. Bypass IN IN to GND with a suitably large capacitor to eliminate noise on the input to the IC. See Input Capacitor. Power Switching Output. SW is the switching node that supplies power to the output. Connect SW the output LC filter from SW to the output load. Note that a capacitor is required from SW to BS to power the high-side switch. GND Ground. Note: Connect the exposed pad to Pin 4. Feedback Input. FB senses the output voltage and regulates it. Drive FB with a resistive voltage FB divider from the output voltage to ground. The feedback threshold is 1.222V. See Setting the Output Voltage. Compensation Node. COMP is used to compensate the regulation control loop. Connect a series COMP RC network from COMP to GND. In some cases, an additional capacitor from COMP to GND is required. See Compensation. Enable Input. EN is a digital input that turns the regulator on or off. Drive EN high to turn on the regulator; low to turn it off. An Under-Voltage Lockout (UVLO) function can be implemented by EN the addition of a resistor divider from VIN to GND. For complete low current shutdown the EN pin voltage needs to be less than 0.7V. For automatic startup leave EN disconnected. Soft-Start Control Input. SS controls the soft-start period. Connect a capacitor from SS to GND SS to set the soft-start period. A 0.1F capacitor sets the soft-start period to 10ms. To disable the soft-start feature, leave SS disconnected. BS
3 4 5
6
7
8
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MP1593 - 3A, 28V, 385KHz STEP-DOWN CONVERTER
OPERATION
IN 2 INTERNAL REGULATORS OSCILLATOR SLOPE COMP CLK CURRENT SENSE AMPLIFIER + -M1 5V
45/385KHz +
1 Q Q
BS
+
S R
1.2V EN 7
--
SHUTDOWN COMPARATOR LOCKOUT COMPARATOR
--
CURRENT COMPARATOR
3 M2 1.8V
SW
-2.60V/ 2.39V
+
+
--
4
GND
FREQUENCY FOLDBACK COMPARATOR
--
0.7V 5
1.22V FB
+
ERROR AMPLIFIER 6 COMP 8 SS
Figure 1--Functional Block Diagram The converter uses an internal N-Channel The MP1593 is a current-mode step-down MOSFET switch to step-down the input voltage regulator. It regulates input voltages from 4.75V to to the regulated output voltage. Since the 28V down to an output voltage as low as 1.22V, MOSFET requires a gate voltage greater than and is able to supply up to 3A of continuous load the input voltage, a boost capacitor connected current. between SW and BS drives the gate. The The MP1593 uses current-mode control to capacitor is internally charged when SW is low. regulate the output voltage. The output voltage An internal 10 switch from SW to GND is used is measured at FB through a resistive voltage to insure that SW is pulled to GND when it is divider and amplified through the internal error low to fully charge the BS capacitor. amplifier. The output current of the transconductance error amplifier is presented at COMP where a network compensates the regulation control system. The voltage at COMP is compared to the internally measured switch current to control the output voltage.
MP1593 Rev. 1.9 9/14/2006
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MP1593 - 3A, 28V, 385KHz STEP-DOWN CONVERTER
APPLICATION INFORMATION
COMPONENT SELECTION
Setting the Output Voltage The output voltage is set using a resistive voltage divider from the output voltage to the FB pin. The voltage divider divides the output voltage down to the feedback voltage by the ratio:
VFB = VOUT R2 R1 + R2
Choose an inductor that will not saturate under the maximum inductor peak current. The peak inductor current can be calculated by:
ILP = ILOAD + VOUT V x 1 - OUT 2 x fS x L VIN
Where ILOAD is the load current. Table 1 lists a number of suitable inductors from various manufacturers. The choice of which inductor to use mainly depends on the price vs. size requirements and any EMI requirement. Table 1--Inductor Selection Guide
Package Dimensions (mm) W 7.0 7.3 5.5 5.5 6.7 L 7.8 8.0 5.7 5.7 6.7 H 5.5 5.2 5.5 5.5 3.0 3.0 3.0 5.1 4.3 4.0 3.0 5.1
Where VFB is the feedback voltage and VOUT is the output voltage. Thus the output voltage is:
VOUT = 1.22 x R1 + R2 R2
R2 can be as high as 100k, but a typical value is 10k. Using that value, R1 is determined by:
R1 = 8.18 x ( VOUT - 1.22)(k )
Vendor/ Model Sumida CR75 CDH74
Core Type Open Open
Core Material Ferrite Ferrite Ferrite Ferrite Ferrite Ferrite Ferrite Ferrite Ferrite Ferrite Ferrite Ferrite
For a 3.3V output voltage, R2 is 10k and R1 is 17k. Inductor The inductor is required to supply constant current to the output load while being driven by the switched input voltage. A larger value inductor will result in less ripple current that will result in lower output ripple voltage. However, larger value inductors will have larger physical size, higher series resistance and/or lower saturation current. A good standard for determining the inductance to use is to allow the inductor peak-to-peak ripple current to be approximately 30% of the maximum switch current limit. Also, make sure that the peak inductor current is below the maximum switch current limit. The inductance value can be calculated by:
L= V VOUT x 1 - OUT fS x IL VIN
CDRH5D28 Shielded CDRH5D28 Shielded CDRH6D28 Shielded CDRH104R Shielded Toko D53LC Type A D75C D104C D10FL Coilcraft DO3308 DO3316 Open Open Shielded Shielded Shielded Open
10.1 10.0 5.0 7.6 9.7 9.4 9.4 5.0 7.6 1.5 13.0 13.0
10.0 10.0
Where VIN is the input voltage, fS is the switching frequency and IL is the peak-to-peak inductor ripple current.
MP1593 Rev. 1.9 9/14/2006
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6
MP1593 - 3A, 28V, 385KHz STEP-DOWN CONVERTER The input capacitor can be electrolytic, tantalum or ceramic. When using electrolytic or tantalum capacitors, a small, high quality ceramic capacitor (i.e. 0.1F) should be placed as close to the IC as possible. When using ceramic capacitors, make sure that they have enough capacitance to provide sufficient charge to prevent excessive voltage ripple at the input. The input voltage ripple caused by the capacitance can be estimated by:
VIN = ILOAD V V x OUT x 1 - OUT fS x C1 VIN VIN
Output Rectifier Diode The output rectifier diode supplies current to the inductor when the high-side switch is off. Use a Schottky diode to reduce losses due to diode forward voltage and recovery times. Choose a diode whose maximum reverse voltage rating is greater than the maximum input voltage, and whose current rating is greater than the maximum load current. Table 2 lists example Schottky diodes and manufacturers. Table 2--Diode Selection Guide
Diode SK33 SK34 B330 B340 MBRS330 MBRS340 Voltage/Current Rating 30V, 3A 40V, 3A 30V, 3A 40V, 3A 30V, 3A 40V, 3A Manufacture Diodes Inc. Diodes Inc. Diodes Inc. Diodes Inc. On Semiconductor On Semiconductor
Output Capacitor The output capacitor is required to maintain the DC output voltage. Ceramic, tantalum or low ESR electrolytic capacitors are recommended. Low ESR capacitors are preferred to keep the output voltage ripple low. The output voltage ripple can be estimated by:
VOUT = VOUT V x 1 - OUT fS x L VIN 1 x R ESR + 8 x f S x C2
Input Capacitor The input current to the step-down converter is discontinuous, therefore a capacitor is required to supply the AC current to the step-down converter while maintaining the DC input voltage. Use low ESR capacitors for the best performance. Ceramic capacitors are preferred, but tantalum or low-ESR electrolytic capacitors will also suffice. Since the input capacitor (C1) absorbs the input switching current it requires an adequate ripple current rating. The RMS current in the input capacitor can be estimated by:
I C1 = ILOAD VOUT VOUT x 1- x VIN VIN

Where L is the inductor value, C2 is the output capacitance value and RESR is the equivalent series resistance (ESR) value of the output capacitor. In the case of ceramic capacitors, the impedance at the switching frequency is dominated by the capacitance, which is the main cause of the output voltage ripple. For simplification, the output voltage ripple can be estimated by:
VOUT = VOUT 8 x fS
2
V x 1 - OUT VIN x L x C2
The worst-case condition occurs at VIN = 2VOUT, where:
IC1 = ILOAD 2
In the case of tantalum or electrolytic capacitors, the ESR dominates the impedance at the switching frequency. For simplification, the output ripple can be approximated to:
VOUT = VOUT V x 1 - OUT fS x L VIN x R ESR
For simplification, choose the input capacitor whose RMS current rating is greater than half of the maximum load current.
The characteristics of the output capacitor also affect the stability of the regulation system. The MP1593 can be optimized for a wide range of capacitance and ESR values.
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MP1593 - 3A, 28V, 385KHz STEP-DOWN CONVERTER Compensation Components The MP1593 employs current mode control for easy compensation and fast transient response. The system stability and transient response are controlled through the COMP pin. COMP is the output of the internal transconductance error amplifier. A series capacitor-resistor combination sets a pole-zero combination to control the characteristics of the control system. The DC gain of the voltage feedback loop is given by:
A VDC = R LOAD x G CS x A VEA x VFB VOUT
In this case (as shown in Figure 3), a third pole set by the compensation capacitor (C6) and the compensation resistor (R3) is used to compensate the effect of the ESR zero on the loop gain. This pole is located at:
f P3 = 1 2 x C6 x R3
The goal of compensation design is to shape the converter transfer function to get a desired loop gain. The system crossover frequency (where the feedback loop has unity gain) is important. Lower crossover frequencies result in slower line and load transient responses, while higher crossover frequencies could cause system instability. A good standard is to set the crossover frequency to approximately one-tenth of the switching frequency. The switching frequency for the MP1593 is 385KHz, so the desired crossover frequency is around 38KHz. Table 3 lists the typical values of compensation components for some standard output voltages with various output capacitors and inductors. The values of the compensation components have been optimized for fast transient responses and good stability at given conditions.
Where AVEA is the error amplifier voltage gain, GCS is the current sense transconductance and RLOAD is the load resistor value. The system has two poles of importance. One is due to the compensation capacitor (C3) and the output resistor of error amplifier, while the other is due to the output capacitor and the load resistor. These poles are located at:
fP1 = fP2 = GEA 2 x C3 x A VEA 1 2 x C2 x R LOAD
Where GEA is transconductance.
the
error
amplifier
The system has one zero of importance, due to the compensation capacitor (C3) and the compensation resistor (R3). This zero is located at:
f Z1 = 1 2 x C3 x R3
The system may have another zero of importance, if the output capacitor has a large capacitance and/or a high ESR value. The zero, due to the ESR and capacitance of the output capacitor, is located at:
fESR = 1 2 x C2 x R ESR
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MP1593 - 3A, 28V, 385KHz STEP-DOWN CONVERTER Table 3--Compensation Values for Typical Output Voltage/Capacitor Combinations
VOUT
1.8V 2.5V 3.3V 5V 12V 1.8 2.5V 3.3V 5V 2.5V 3.3V 5V 12V
Determine C3 by the following equation:
C3 > 4 2 x R3 x f C
L
4.7H 4.76.8H 6.810H 1015H 1522H 4.7H 4.76.8H 6.810H 1015H 4.76.8H 6.810H 1015H 1522H
C2
100F Ceramic 47F Ceramic 22Fx2 Ceramic 22Fx2 Ceramic 22Fx2 Ceramic 100F SP-CAP 47F SP-CAP 47F SP-CAP 47F SP CAP 560F Al. 30m ESR 560F Al 30m ESR 470F Al. 30m ESR 220F Al. 30m ESR
R3
5.6k 3.9k 5.6k 7.5k 10k 5.6k 4.7k 6.8k 10k 10k 10k 15k 15k
C3
3.3nF 5.6nF 8.2nF 10nF 3.3nF
C6
None None None None None
Where R3 is the compensation resistor value. 3. Determine if the second compensation capacitor (C6) is required. It is required if the ESR zero of the output capacitor is located at less than half of the 385KHz switching frequency, or the following relationship is valid:
f 1 3.3nF 100pF 5.6nF 10nF 10nF 5.6nF 8.2nF 5.6nF None None None 1.5nF 1.5nF 1nF
Where C2 is the output capacitance value, RESR is the ESR value of the output capacitor and fS is the switching frequency. If this is the case, then add the second compensation capacitor (C6) to set the pole fP3 at the location of the ESR zero. Determine C6 by the equation:
C6 = C2 x R ESR R3
Where C2 is the output capacitance value, RESR is the ESR value of the output capacitor and R3 is the compensation resistor. External Bootstrap Diode It is recommended that an external bootstrap diode be added when the system has a 5V fixed input or the power supply generates a 5V output. This helps improve the efficiency of the regulator. The bootstrap diode can be a low cost one such as IN4148 or BAT54.
5V
4.7nF 390pF
To optimize the compensation components for conditions not listed in Table 3, the following procedure can be used. 1. Choose the compensation resistor (R3) to set the desired crossover frequency. Determine R3 by the following equation:
R3 = 2 x C2 x f C VOUT x G EA x G CS VFB
BS
1
Where fC is the desired crossover frequency (which typically has a value no higher than 38KHz). 2. Choose the compensation capacitor (C3) to achieve the desired phase margin. For applications with typical inductor values, setting the compensation zero, fZ1, below one forth of the crossover frequency provides sufficient phase margin.
MP1593
SW 3
10nF
Figure 2--External Bootstrap Diode This diode is also recommended for high duty cycle operation (when
VOUT >65%) and high VIN
output voltage (VOUT>12V) applications.
MP1593 Rev. 1.9 9/14/2006
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MP1593 - 3A, 28V, 385KHz STEP-DOWN CONVERTER
TYPICAL APPLICATION CIRCUITS
INPUT 4.75V to 28V C5 10nF
OFF ON
7
2 IN EN
1 BS 3 SW
OUTPUT 2.5V 3A
MP1593
8 SS GND 4 FB COMP 6 5
C6
(optional)
C3 3.3nF
D1 B340A
Figure 3--MP1593 with AVX 47F, 6.3V Ceramic Output Capacitor
C5 10nF
INPUT 4.75V to 28V
OFF ON
2 IN 7 EN
1 BS 3 SW
OUTPUT 2.5V 3A
MP1593
8 SS GND 4 FB COMP 6 5
C6
(optional)
C3 3.3nF
D1 B340A
Figure 4--MP1593 with Panasonic 47F, 6.3V Special Polymer Output Capacitor
MP1593 Rev. 1.9 9/14/2006
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MP1593 - 3A, 28V, 385KHz STEP-DOWN CONVERTER
PACKAGE INFORMATION
SOIC8E (EXPOSED PAD)
0.189(4.80) 0.197(5.00) 8 5 0.124(3.15) 0.136(3.45)
PIN 1 ID
0.150(3.80) 0.157(4.00)
0.228(5.80) 0.244(6.20)
0.089(2.26) 0.101(2.56)
1
4
TOP VIEW
BOTTOM VIEW
SEE DETAIL "A" 0.051(1.30) 0.067(1.70) SEATING PLANE 0.000(0.00) 0.006(0.15) 0.050(1.27) BSC
0.0075(0.19) 0.0098(0.25)
0.013(0.33) 0.020(0.51)
SIDE VIEW
FRONT VIEW
GAUGE PLANE 0.010(0.25) BSC
0.010(0.25) x 45o 0.020(0.50)
0.024(0.61)
0.050(1.27) 0o-8o 0.016(0.41) 0.050(1.27)
0.063(1.60)
DETAIL "A"
0.103(2.62)
0.213(5.40)
NOTE:
1) CONTROL DIMENSION IS IN INCHES. DIMENSION IN BRACKET IS IN MILLIMETERS. 2) PACKAGE LENGTH DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. 3) PACKAGE WIDTH DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. 4) LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.004" INCHES MAX. 5) DRAWING CONFORMS TO JEDEC MS-012, VARIATION BA. 6) DRAWING IS NOT TO SCALE.
0.138(3.51)
RECOMMENDED LAND PATTERN
NOTICE: The information in this document is subject to change without notice. Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MPS products into any application. MPS will not assume any legal responsibility for any said applications.
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